Design methodology

Figure 1 illustrates the complete schematic of the on-chip spherical DR-fed RCA with eight input ports. The antenna is constructed from three distinct layers of PCB: the bottom layer made of Rogers RT6202 ( $\varepsilon_r = 2.94$ and $\tan\delta = 0.0015$),  $0.508\,\mathrm{mm}$ thick middle board of Rogers RT5880 ( $\varepsilon_r = 2.2$ and $\tan\delta = 0.0009$), and the top printed superstrate layer of Rogers TMM4 ( $\varepsilon_r = 4.5$ and $\tan\delta = 0.002$). Four circular crates are precisely machined into the top of the chip layer to accommodate the four DRs. The middle board is then positioned on top, featuring square metallic patches with circular slots. These slots are aligned directly above the crates, ensuring that the dielectric spheres fit securely between the crates in the chip layer and the slots in the middle board. Screws and spacers are installed at each of the four corners of the antenna. The screws pass through the holes in the spacers and are tightened to press the dielectric spheres firmly against the chip. This setup ensures that the DRs remain firmly in place and do not dislocate during installation or operation. By doing so, the non-radiant modes of the DRs are excited, with the $\mathrm{TE}_{112}$ mode providing the strongest coupling to the chip [Reference López Cuenca8]. The resonance frequency of the DRs is determined using Equation (1):

(1)\begin{align} f_\mathrm{res}~(\mathrm{GHz}) = \frac {a}{d~\mathrm{(mm)}}, \end{align}

where d is the diameter of the spherical DR. The constant a is specific to the modes and is determined by the effective dielectric constant of the DR.

For this design, the DR is made of alumina ( $\mathrm{Al}_2\mathrm{O}_3$), which has a dielectric constant of 9.8 and a low loss tangent of less than 0.001 up to a frequency of  $100\,\mathrm{GHz}$. The parameter a is 104.3 for the $\mathrm{TE}_{112}$ mode [Reference Alberto González Marín9]. At the operating frequency of  $30\,\mathrm{GHz}$, the diameter of the DR is approximately  $3.5\,\mathrm{mm}$, considering that the middle board on top of the spheres excites the $\mathrm{TE}_{112}$ mode. To enable power combination within the antenna, the non-radiating $\mathrm{TE}_{112}$ mode which exhibits electric symmetry is excited from two different directions by two diagonally opposite microstrip resonators each measuring $\frac{\lambda_{g}}{4}$ in length, where λ_g is the guided wavelength. These resonators are probe-fed with equal amplitudes and a phase difference of 180^∘ using SMPM-type RF coaxial connectors [10]. Four circular coupling slots on the lower ground layer of the middle board located above each spherical DR facilitate the coupling of the non-radiating modes of each DR to the microstrip patch radiator on the top layer of the middle board.

A printed PRS board is positioned at height L_r above the middle board, forming a resonant cavity. This configuration allows the EM fields to undergo multiple reflections, which leads to resonance and enhances the antenna’s directivity and overall radiation performance. The value of L_r is calculated from [Reference Feresidis, Goussetis, Wang and Vardaxoglou11] according to Equation (2):

(2)\begin{align} \frac{4\pi L_{r} }{\lambda_{0}} = 2N\pi - \phi_{\mathrm{ground}} - \phi_{\mathrm{PRS}}, \end{align}

where λ ₀ represents the free space wavelength at the operating frequency, N is the vertical wave number, $\phi_{\mathrm{ground}}$ and $\phi_{\mathrm{PRS}}$ are the phase delays introduced in the electric field after reflection from the ground and the PRS, respectively. We assume that $\phi_{\mathrm{ground}} = \phi_{\mathrm{PRS}} = -\pi$. Hence, the smallest cavity length for fundamental resonance is $L_{r} = \frac{\lambda_{0}}{2}$ [Reference Baba, Hashmi, Esselle, Gonzalez Marin and Hesselbarth12].

Figure 1(a) displays an isometric view of the antenna model, including an expanded back view of the thin printed PRS. Alongside creating a resonant cavity in the antenna, the printed PRS also creates a more uniform aperture phase distribution above the patch radiators. The PRS is composed of Rogers $\mathrm{TMM}4$ with circular metallic patches printed on the underside facing the patch radiators. The diameters of the circular metallic patches ( $D1$, $D2$, $D3$, $D4$, and $D5$) printed on the bottom side of the PRS decrease gradually from the center toward the edge. This configuration adds more phase delay to the field at the center compared to the edges. The PRS plays a crucial role in determining the antenna’s radiation properties, including directivity and radiation pattern. For more detailed information on the design of printed PRS, readers are referred to [Reference Baba, Hashmi, Esselle, Gonzalez Marin and Hesselbarth12].

Figure 1.

Design configuration of the on-chip multi-feed resonant cavity antenna system. (a) Isometric view of the antenna simulation model showing an expanded back view of the PRS [Reference Singh, Attygalle, Thalakotuna and Esselle7] and (b) expanded view of a DR, coupling slot, and alignment hole, DR fed by two microstrip resonators and the feed topology of the complete antenna [Reference Singh, Attygalle, Thalakotuna and Esselle7].

Figure 2 illustrates the feeding arrangement used to excite the DRs, which are mounted on top of the circuit board shown in Figure 1(a). Each of the DRs (in bronze) is fed by two microstrip resonators (in red and black) located diagonally opposite. These microstrip resonators are probe-fed with equal amplitudes and a phase difference of 180^∘ using SMPM-type RF coaxial connectors [10]. This arrangement excites the same non-radiating modes from two different directions, achieving constructive power combining. Additionally, four coupling slots are incorporated into the lower ground layer of the middle board to facilitate the coupling of the non-radiating modes of each DR to the microstrip patch radiator positioned on the top layer directly above each spherical DR.

Figure 2.

Bottom view of the antenna showing the microstrip resonator feed pairs (black) and (red) and DRs (bronze). Feed pairs $(1, 2), (3, 4), (5, 6)$, and $(7, 8)$ feed DRs- $1, 2, 3 $, and 4, respectively [Reference Singh, Mulinde, Attygalle, Thalakotuna and Esselle13].

Simulation results

The proposed eight-input RCA was modeled in CST MWS, and full-wave EM simulations were conducted using the time domain solver. Figure 3 shows the simulated return loss for each input port (when all ports are excited simultaneously). The antenna demonstrates excellent matching, with a return loss of less than  $-8\,\mathrm{dB}$ across all eight input ports within the frequency range of 28.8– $32.5\,\mathrm{GHz}$. The weak coupling of the feeding elements arises from signal leakage from the edges to the top, which enables the integration of multiple feeding DRs within the same chip area without impacting the input impedance of the feeds. An outstanding in-antenna power combination is achieved by exciting the same non-radiating resonance modes in each feeding DR. Figure 4 shows the simulated radiation pattern for each individual DR (see Figure 4(a)) as well as the radiation pattern for the overall antenna system at  $30\,\mathrm{GHz}$ (see Figure 4(b)).

Figure 3.

Simulated return loss at each input port of the antenna [Reference Singh, Attygalle, Thalakotuna and Esselle7].

Figure 4.

Simulated realized gain pattern for the 8-port RCA at  $30\,\mathrm{GHz}$ [Reference Singh, Mulinde, Attygalle, Thalakotuna and Esselle13]. (a) Individual DRs. (b) Antenna system.

Figure 5(a) illustrates the variations in the simulated directivity and realized antenna gain over frequency when each DR is excited individually. The variations in gain and directivity are consistent with the reciprocal behavior of the antenna. Specifically, odd-numbered, $\mathrm{DR}1$ and $\mathrm{DR}3$ exhibit similar and closely matching responses, while even-numbered, $\mathrm{DR}2$ and $\mathrm{DR}4$ also display similar and closely matching responses. Figure 5(b) shows the simulated directivity and realized gain variation of the antenna system over the same frequency range, with and without the printed PRS. It can be observed that the PRS increases the overall directivity and realized gain of the antenna. A peak gain enhancement of approximately  $10\,\mathrm{dB}$ is achieved at the design frequency of  $30\,\mathrm{GHz}$. A maximum simulated directivity of  $20.1\,\mathrm{dB}$ and a maximum realized gain of  $19.4\,\mathrm{dB}$ at  $30\,\mathrm{GHz}$ are achieved. The  $3\,\mathrm{dB}$ gain bandwidth of the antenna is approximately  $1.9\,\mathrm{GHz}$ from  $28.9\,\mathrm{GHz}$ to $30.8\,\mathrm{GHz}$. Figure 5(b) also shows the maximum sidelobe levels against frequency. The sidelobes are consistently below  $-10\,\mathrm{dB}$ across the frequency range of 28.18– $31.45\,\mathrm{GHz}$.

Figure 5.

Simulated radiation characteristics for the 8-port RCA at boresight, with directivity (solid) and gain (dashed). (a) Individual DRs. (b) Gain, directivity, and sidelobe level over frequency for the antenna system.

Figure 6(a) compares the radiation efficiency between the proposed antennas with and without the PRS. The radiation efficiency of the antenna featuring the PRS remains largely comparable to that of the antenna without it, showing only a slight decrease of about 2% within the frequency range of 28– ${29}\,\mathrm{GHz}$. It was observed that the radiation efficiency exceeds 93.3% and the total efficiency remains above 81.6% across the frequency range of 28.8– $32.6\,\mathrm{GHz}$. A $3\mathrm{D}$ radiation pattern obtained at 30 GHz is presented as an inset in Figure 6(a).

Figure 6.

Characteristics of the multi-feed RCA. (a) Radiation efficiency plots with and without the PRS [Reference Singh, Attygalle, Thalakotuna and Esselle7] featuring a 3D radiation pattern at 30 GHz shown as an inset. (b) Elevation radiation pattern cut for different frequencies at $\phi = 0^{\circ}$.

To demonstrate the radiation pattern characteristics of the designed antenna, the elevation-plane radiation pattern for the antenna is illustrated for five different frequencies within the operating band in Figure 6(b). The maximum realized gain occurs at the design frequency of  $30\,\mathrm{GHz}$.

Antenna fabrication, measurement, and experimental results

Following the design description in Design methodology section, a prototype of the on-chip DR-fed RCA with eight inputs was fabricated and measured. The design parameters are provided in Table 1, and a comparison between the measured and simulated return loss at each port is shown in Figure 7. The thickness of the conductor on the middle board is  $0.035\,\mathrm{mm}$ and is  $0.017\,\mathrm{mm}$ on the PRS and the circuit board. The side length of all the square boards and the brass plate is $O = 45\,\mathrm{mm}$. A strategic approach has been adopted to assemble the antenna, ensuring that the DRs are secured tightly. The three separately fabricated boards (circuit board, middle board, and the PRS) are assembled with the spherical DRs and a supporting brass plate using nylon spacers and polyvinylidene fluoride plastic screws. Through holes were drilled on the boards and brass plate to provide passage for screws during assembly and packaging. The three boards are aligned accurately by inserting plastic screws, and proper spacing between the layers is maintained using $3\mathrm{D}$-printed nylon spacers. The nylon spacers have through holes to allow the screws to pass. A  $2.5\,\mathrm{mm}$ thick brass plate is positioned beneath the circuit board to enhance the design’s sturdiness and durability, especially given the circuit board’s thickness of just  $0.508\,\mathrm{mm}$. This added support helps to prevent flexing and ensures structural integrity, thereby contributing to the overall reliability of the assembly. The brass plate further acts as a cover for the alignment holes on the substrate, preventing radiation leakage. The assembly process is pictorially illustrated in Figure 8. First, plastic screws are inserted into the four corner holes of the brass plate, providing a secure foundation.

Figure 7.

Measured and simulated return loss at (a) port 1 to port 4 (S11, S22, S33, S44) and (b) port 5 to port 8 (S55, S66, S77, and S88).

Figure 8.

Fabricated components: circuit board (top left), brass plate (top right), DRs positioned on the crate within the circuit board and $3\mathrm{D}$-printed nylon spacers (bottom left), assembly and packaging of the RCA.

Table 1.

Design parameter values for the proposed antenna [Reference Singh, Attygalle, Thalakotuna and Esselle7]

The bottom circuit board is then placed directly on top of the brass support layer, with the four corner holes aligned over the screw legs at each corner, allowing it to slide into position. To maintain an appropriate gap between the middle layer and the circuit board, four nylon spacers with center-through holes are added, one at each screw location, by sliding them over the screw legs. Next, four spherical DRs are positioned on the four crates within the circuit board. The middle board is then placed, allowing its corners to slide over the same screw legs at each corner. Another set of four nylon spacers is added, one at each corner, by sliding them over the screw legs. These spacers create the necessary height to form a resonant cavity. Finally, the PRS is added, with its four corner holes aligned with the same four screw legs at each corner. Bolts are used to fasten the screws, ensuring that the assembly is secure and prevents displacement of the spheres after packaging. This careful assembly process enhances both stability and performance in the final design.

While Figure 8 displays the fabricated components and the assembled antenna prototype, Figure 9 shows the RCA installed in a $3\mathrm{D}$-printed antenna mount, and the high-frequency RF cables that were connected to each input port. S-parameters were measured using a multi-port vector network analyzer (VNA) (Figure 7). The measured return loss at all ports, except for port- $1~(\mathrm{S}11)$, is below  $-8\,\mathrm{dB}$ between  $27.8\,\mathrm{GHz}$ and $30.7\,\mathrm{GHz}$. For port 1, the return loss goes up to  $-6\,\mathrm{dB}$ between  $27.6\,\mathrm{GHz}$ and $28.8\,\mathrm{GHz}$ but remains below  $-8\,\mathrm{dB}$ from  $28.8\,\mathrm{GHz}$ to $30.2\,\mathrm{GHz}$. The variation in port-1 matching could be due to lossy cables. To ensure consistent measurement of the multi-input antenna, we validate the results using the following three different measurement setups.

Figure 9.

Assembled RCA with a $3\mathrm{D}$-printed mount.

• • Measurement setup I: a 2-port VNA is used for obtaining the gain for each DR. The transmit path to each DR is identical.

• • Measurement setup II: a 2-port VNA is used for obtaining the gain for each DR. However, different transmit paths are used while testing each DR.

• • Measurement setup III: a multichannel arbitrary waveform generator (AWG) is used to simultaneously excite all DRs via different transmit paths.

Individual DR excitation

We investigate the performance of the antenna with individual DR excitation using measurement setups I and II.

Measurement setup I

A schematic for the transmit chain used for performing measurements with independent individual excitations is shown in Figure 10.

Figure 10.

Transmit chain setup for individual DR – measurement setup I.

A 2-port VNA was used to characterize the transmission path from the signal generator to the receiver. This same transmission path is used for studying the behavior of each DR. In this transmit chain (Figure 12(a)), a single channel signal generator feeds a power amplifier (PA). The output of the PA feeds the input port of a phase shifter. The pair of outputs from the phase shifter, with a phase difference of 180^∘ in turn, excite each individual DR of the RCA. While each DR was excited, the other six input ports of the RCA that feed the rest of the DRs were terminated using  $50\,\mathrm{dB}$ matched loads. A single channel signal generator, therefore, excites each spherical DR (see Figure 10). In measurement setup I, for characterizing each individual DR, the output power from the single channel signal generator was set to $0~\mathrm{dBm}$. A standard gain horn (SGH) antenna was used to collect the signal at the receiver side. The antenna gain corresponding to each DR was measured and is shown in Figure 11(a) and (b). Figure 11(a) plots the elevation plane radiation pattern cut for each DR at a center frequency of  $30\,\mathrm{GHz}$ as measured in an anechoic chamber. The main lobes for $\mathrm{DR}1$, $\mathrm{DR}2$, $\mathrm{DR}3$, and $\mathrm{DR}4$ exhibit peaks at  $9.74\,\mathrm{dB}$,  $9.49\,\mathrm{dB}$,  $10.58\,\mathrm{dB}$, and  $10.09\,\mathrm{dB}$, respectively with corresponding offsets from boresight at  $-3^{\circ}$, 9^∘, 0^∘, and 10.0^∘, respectively.

Figure 11.

Measured radiation performance of the RCA with individual DR excitation with measurement setup I. (a) Elevation plane radiation pattern cut at  $30\,\mathrm{GHz}$. (b) Peak gain vs frequency.

Figure 12.

Transmit chains for multiple DRs. (a) Measurement setup II. (b) Measurement setup III.

Figure 11(b) shows the measured peak gain against frequency for each DR in the 28– $32\,\mathrm{GHz}$ frequency range. The peak gains for $\mathrm{DR}1$, $\mathrm{DR}2$, $\mathrm{DR}3$, and $\mathrm{DR}4$ are  $10.59\,\mathrm{dB}$,  $10.06\,\mathrm{dB}$,  $10.76\,\mathrm{dB}$, and  $10.09\,\mathrm{dB}$ at frequencies of  $30.5\,\mathrm{GHz}$,  $30.5\,\mathrm{GHz}$,  $30.5\,\mathrm{GHz}$, and  $30\,\mathrm{GHz}$, respectively. In this frequency range, $\mathrm{DR}3$ exhibits the highest peak gain of 10.76 at  $30.5\,\mathrm{GHz}$, while $\mathrm{DR}2$ exhibits the lowest peak gain of 10.06 at  $30.5\,\mathrm{GHz}$.

Figure 13.

Measured radiation performance of the RCA with individual DR excitation using measurement setup II. (a) Elevation plane radiation pattern cut at  $30\,\mathrm{GHz}$. (b) Peak gain vs frequency.

Measurement setup II

The setup for the transmit chain illustrated in Figure 12(a) was used to investigate the performance of each DR with independent transmit paths. The results from these measurements are presented in Figure 13. Figure 13(a) plots the elevation plane radiation pattern cut for each DR of the RCA at a center frequency of  $30\,\mathrm{GHz}$. The main lobes for $\mathrm{DR}1$, $\mathrm{DR}2$, $\mathrm{DR}3$, and $\mathrm{DR}4$ exhibit peaks at  $10.16\,\mathrm{dB}$,  $10.45\,\mathrm{dB}$,  $10.56\,\mathrm{dB}$, and  $10.67\,\mathrm{dB}$, respectively, with corresponding offsets from boresight at  $-1.5^{\circ}$, 8^∘, 1^∘, and 9^∘, respectively.@@@

Figure 13(b) shows the measured peak gain against frequency for each DR in the 28– $32\,\mathrm{GHz}$ frequency range. The peak gains for $\mathrm{DR}1$, $\mathrm{DR}2$, $\mathrm{DR}3$, and $\mathrm{DR}4$ are  $11.36\,\mathrm{dB}$,  $10.97\,\mathrm{dB}$,  $11.56\,\mathrm{dB}$, and  $10.78\,\mathrm{dB}$ at frequencies of  $30.5\,\mathrm{GHz}$,  $30.5\,\mathrm{GHz}$,  $30\,\mathrm{GHz}$, and  $30.5\,\mathrm{GHz}$, respectively. In this frequency range, $\mathrm{DR}3$ exhibits the highest peak gain of 11.56 at  $30\,\mathrm{GHz}$, while $\mathrm{DR}4$ exhibits the lowest peak gain of 10.78 at  $30.5\,\mathrm{GHz}$.

Simultaneous DR excitation

In measurement setup III (Figure 12(b)), a four-channel AWG was used to excite the four DRs of the RCA. Subsequently, each of the four synchronized outputs of the AWG feeds a PA whose output, in turn, feeds each of the four phase shifters. The resulting eight signals from the output ports of the phase shifters feed the 8-port RCA by simultaneously exciting all four DRs.

The experimental setup for the multichannel transmit chain is shown in Figure 12(b). The transmit power from each of the four output ports of the AWG was set to be four times less ( $-6~\mathrm{dBm}$) compared to measurement setups I and II. This power level corresponds to a peak-to-peak voltage of  $0.31698\,\mathrm{dB}$. Similar to measurement setups I and II, an SGH antenna was used as a receiver. The measured elevation plane radiation pattern cuts for frequencies 29– $31\,\mathrm{GHz}$ are shown in Figure 14(a). The highest peak gain of about  $11.37\,\mathrm{dB}$ is observed with an offset of 3^∘ at  $30\,\mathrm{GHz}$. The maximum gain shows the least value of about  $5.91\,\mathrm{dB}$ at  $29\,\mathrm{GHz}$ with an offset of 2^∘. The side lobes at  $30\,\mathrm{GHz}$ are about  $16\,\mathrm{dB}$ below the peak value. The highest sidelobes are observed at  $30.5\,\mathrm{GHz}$ and  $31\,\mathrm{GHz}$. A  $3\,\mathrm{dB}$ beam width of about 17^∘ is observed at  $30\,\mathrm{GHz}$ in Figure 14(a). Figure 15 shows the equivalent polar plot for the measured gain of the multi-feed RCA for frequencies from  $29\,\mathrm{GHz}$ to $31\,\mathrm{GHz}$.

Figure 14.

Radiation performance of the RCA with simultaneous DR excitation using measurement setup III. (a) Elevation plane radiation pattern cuts for 30– $31\,\mathrm{GHz}$. (b) Gain vs frequency.

Figure 15.

Measured polar plots for the gain of the RCA at five different frequencies.

Figure 14(b) shows the measured gain versus frequency plot for the multi-feed RCA for the frequency range 28– $32\,\mathrm{GHz}$ at boresight as measured in an anechoic chamber. A maximum gain of about  $11.2\,\mathrm{dB}$ is observed with a  $3\,\mathrm{dB}$ bandwidth of about  $2.0\,\mathrm{GHz}$. The highest measured gain is observed to be at  $30\,\mathrm{GHz}$, which is consistent with the observations from Figure 14(a).

Analysis and discussion of results

Individual DR excitation

We compare the simulated results for individual DR excitation with the experimental results obtained using measurement setup I and measurement setup II. First, we compare the elevation plane radiation pattern cuts at  $30\,\mathrm{GHz}$. We then compare the simulated gain against frequency plots for individual DRs with the measured results. These key results for radiation pattern and gain against frequency plots are summarized in Table 2, later in this article.

Table 2.

Summary of key results from simulation, measurement setups I and II

Elevation plane radiation pattern cuts

The simulated elevation plane radiation pattern cuts at  $30\,\mathrm{GHz}$ are shown in Figure 4(a) while the equivalent measured results from measurement setup I are shown in Figure 11(a). The measured results for measurement setup II are shown in Figure 13(a).

The peak gains for each DR in both the simulated and measured results at  $30\,\mathrm{GHz}$ have offsets on similar sides with respect to 0^∘ (i.e., $\mathrm{DR}1$ and $\mathrm{DR}3$ are on the same side, while $\mathrm{DR}2$ and $\mathrm{DR}4$ have offsets on the opposite side of 0^∘). While the observed offsets for these peaks exhibit symmetry in the simulated results (see Figure 4(a)), the symmetry in measured results degrades with measurement setup I exhibiting more symmetry compared to measurement setup II. The extra degradation in symmetry observed in the results for measurement setup II is because in measurement setup I, the same signal transmit path is the same for each DR, whereas the signal paths are different in measurement setup II.

In the simulated results (see Figure 4(a)), the peak gains for $\mathrm{DR}2$ and $\mathrm{DR}3$ are slightly higher by about  $0.33\,\mathrm{dB}$ compared to $\mathrm{DR}1$ and $\mathrm{DR}4$. The offsets for $\mathrm{DR}1$ and $\mathrm{DR}4$ are at  $-1.5^{\circ}$ and 1.5^∘ respectively, while the offsets for $\mathrm{DR}2$ and $\mathrm{DR}3$ are at 1.0^∘ and  $-1.0^{\circ}$ respectively.

In the results from measurement setup I (Figure 11(a)), the peak gains for $\mathrm{DR}3$ and $\mathrm{DR}4$ are slightly higher by up to $1\,\mathrm{dB}$ compared to $\mathrm{DR}1$ and $\mathrm{DR}2$. The offsets for $\mathrm{DR}1$ and $\mathrm{DR}2$ are on opposite sides with respect to those of $\mathrm{DR}3$ and $\mathrm{DR}4$ and closely resemble the simulation results. The offsets, however, are much bigger, and the axis of symmetry for the main beams of all the DRs is no longer at 0^∘.

In the results from measurement setup II (Figure 13(a)), the peak gain for $\mathrm{DR}3$ is highest, by about $1\,\mathrm{dB}$ compared to  $\mathrm{DR}1$,  $\mathrm{DR}2$, and $\mathrm{DR}4$, which have comparable peaks. The offsets for $\mathrm{DR}1$ and $\mathrm{DR}2$ are also on opposite sides of the axis of symmetry with respect to the offsets for $\mathrm{DR}3$ and $\mathrm{DR}4$. This observation is similar to the results from simulation and measurement setup I with relatively minor variations. This deviation of results in measurement setup I from those obtained using measurement setup II can be attributed to the variations across the four transmit paths in measurement setup II. It should be noted that the characteristics for $\mathrm{DR}1$ are the most consistent across measurement setups I and II since this transmit path for $\mathrm{DR}1$ does not change across the two measurement setups.

Gain vs frequency plots

With individual DR excitation, we compare the simulated gain against frequency results in Figure 5(a), with the experimental results using measurement setup I in Figure 11(b) and measurement setup II in Figure 13(b). Across Figures 5(a), 11(b), and 13(b), gain against frequency plots exhibit similar trends. Results from measurement setup II (see Figure 13(b)) show a distinct variation in gain for $\mathrm{DR}3$ being visibly higher than in measurement setup I (Figure 11(b)). This is attributed to the characteristic of the amplifier on the transmit path for $\mathrm{DR}3$ (see Figure 16). The gain for amplifier 3 is consistently higher (by about  $0.25\,\mathrm{dB}$) compared to the rest of the amplifiers, over the frequency range 29.2– $31.1\,\mathrm{GHz}$.

Figure 16.

Amplifier gain vs frequency.

Simultaneous DR excitation

We compare the simulated results for simultaneous DR excitation with the experimental results using measurement setup III. First, we compare the simulated elevation plane radiation pattern cuts. We then compare the simulated gain against frequency plots with the measured results. The key radiation pattern and gain against frequency results for simultaneous excitation are summarized in Table 3.

Table 3.

Summary of key RCA results from simulation, measurement setup III

*The reflection at port 1 is below  $-6\,\mathrm{dB}$ for the frequency range 27.6– $28.5\,\mathrm{GHz}$ and is below  $-8\,\mathrm{dB}$ for 28.5– $30.2\,\mathrm{GHz}$.

Elevation plane radiation pattern cuts

The measured radiation patterns for multiple frequencies from  $29\,\mathrm{GHz}$ to $31\,\mathrm{GHz}$ are shown in Figure 14(a) while the simulated elevation plane radiation patterns are shown in Figures 4(a) and 6(b). Measured polar plots of gain at five different frequencies are shown in Figure 15. In both simulated and measured results, we observe that the highest gain occurs at the intended design frequency of  $30\,\mathrm{GHz}$, while the lowest gain occurs at  $29\,\mathrm{GHz}$.

Gain vs frequency plots

The plots for the measured gain against frequency are shown in Figure 14(b), while the simulated results are presented in Figure 5(b). Across Figures 5(b) and 14(b), the plots exhibit similar trends.